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? introduction: ? fea tures: the /5 is a high-frequency boost converter dedicated for small to medium lcd bias supply and white led backlight supplies. the device is ideal to generate output voltages up to 28v from a dual cell nimh/nicd or a single cell li-ion battery. the part can also be used to generate standard 3.3v/5v to 12v power conversions. the /5 operates with a switching frequency up to 1mhz. this allows the use of small external components using ceramic as well as tantalum output capacitors. together with the small package, the /5 gives a very small overall solution size. the /5 has an internal 400ma switch current limit, offering low output voltage ripple and allows the use of a small form factor inductor for low power applications. the low quiescent current (20 a typ) together with an optimized control scheme, allows device operation at very high efficiencies over the entire load current range. the /5 is available in dfn22-6, sot23-6 sot23-5 packages. it operates over an ambient temperature range of -40 to + 8 5 . z input voltage range: 2.0v to 5.5v z adjustable output voltage range up to 28v z 400ma internal switch current z up to 1mhz switching frequency z 20 a typical no load quiescent current z 0.1 a typical shutdown current z internal soft-start function z -40 to +85 operating temperature range z available in green dfn22-6, sot23-6 and sot23-5 packages ? applica tions ? ? z lcd bias supply z white-led supply for lcd backlights z digital still camera z pdas, organizers, and handheld pcs z cellular phones z internet audio player z standard 3.3v/5v to 12v conversion low power dc-dc step-up converter /5 series ? ordering informa tion /5 7 8 designator symbol description 7 a standard 8 e package:sot23-6 fb6 package:dfn2x2-6 m package:sot23-5 leshan radio company, ltd. 9hu
? typical application circuit sw v ss fb 10 h 10k ? /5 en r1 r2 c out 1 f d1 v in c ff c in 4. 7 f v out = v in to 2 8v v in = 2.0v to 5.5 v figure 1 standard application circuit ? pin configura tion s ot23-6 sot23-5 dfn2x2-6 top view top view top view pin description sot23-6 sot23-5 dfn2x2-6 name e m fb6 fb6b 3 1 6 4 sw switch pin . switch pin. it is connected to the drain of the internal power mosfet. connect this pin to the inductor and schottky diode. 4 2 1 3 gnd ground 6 3 4 1 fb feedback pin . feedback pin. connect this pin to the external voltage divider to program the desired output voltage. 2 4 3 5 en chip enable . enable pin. pulling this pin to ground forces the device into shutdown mode reducing the supply current to less than 1 a. this pin should not be left floating and needs to be terminated. 1 5 2 6 vin chip supply pin . power supply. must be closely decoupled to gnd with a capacitor 5 - 5 2 nc no connection - - 7 7 exposed pad power ground exposed pad. must be connected to gnd plane. leshan radio company, ltd.
? absolut e maximum ratings (unless otherwise specified, t a = 25c) (1) p arameter symbol ratings units supply v oltage range v in -0.3~7 v sw switch voltage 32 v en, fb, voltage -0.3~v in v power dissipation sot23-5 p d 400 mw dfn2x2-6 500 mw sot23-6 400 mw operatin g temperature range -40~85 operating junction temperature range t j 150 storage t emperature t stg - 65~150 lead temperature(soldering, 10 sec) t solder 260 esd rating (5) human body model - (hbm) 4000 v machine model- (mm) 250 v note: stresses beyond those listed under ?absolute maximum ratings? may cause permanent damage to the device. these are stress ratings only, and functional operation of the device at these or any other conditions beyond those indicated in the operational sections of the specifications is not implied. exposure to absolute maximum rating conditions for extended periods may affect device reliability. caution t his integrated circuit can be damaged by esd if you don?t pay attention to esd protection. chipower recommends that all integrated circuits be handled with appropriate precautions. failure to observe proper handling and installation procedures can cause damage. esd damage can range from subtle performance degradation to complete device failure. precision integrated circuits may be more susceptible to damage because very small parametric changes could cause the device not to meet its published specifications. leshan radio company, ltd.
? electrical characteristics (v in = 2.4v, en = v in , c in = 4.7 f, c out = 1 f, l = 10 h, t a = - 40 to +85 . typical values are at t a = +25 , unless otherwise noted.) parameter symbol conditions min typ (1) max units suppl y input supply range v in 2.0 5.5 v shutdown current i sd en = gnd 0.1 1 a operating quiescent current i q i out = 0ma, not switching, v fb = 1.3v 20 35 a unde r-voltage lockout threshold v uvlo 1.5 1.65 v enable en input high v oltage v ih 1.5 v en input low v oltage v il 0.4 v en input lea kage current en=gnd or v in 0.1 1 a power switch and current limit maximum switch v oltage v sw 29 v minimum of f time t off 270 430 570 ns maximum on time t on 4 6 8.5 s mosfet on-resistance r ds(on) v in = 2.4v , i sw = 200ma 660 1100 m mosfet leakage current v sw = 28v 1 a switch curre nt limit i lim 210 400 500 ma output adjustable o utput voltage range v out v in 28 v feedb ack reference voltage v fb t a = 25 1.182 1.202 1.223 v feedback leakage current i fb v fb = 1.3v 1 a leshan radio company, ltd.
? typical perform ance characteristics (t a =2 5 , unless otherwise specified, test figure1 above) leshan radio company, ltd.
? typical performance characteristics (t a =2 5 , unless otherwise specified, test figure1 above) leshan radio company, ltd.
? detailed description the /5 operates with an input voltage range of 2.0v to 5.5v and can generate output voltages up to 28v. the device operates in a pulse-frequency modulation (pfm) scheme with constant peak current control. this control scheme maintains high efficiency over the entire load current range, and with a switching frequency up to 1mhz, the device enables the use of very small external components. the convert er monitors the output voltage, and as soon as the feedback voltage falls below the reference voltage of typically 1.202v, the internal switch turns on and the current ramps up. the switch turns off as soon as the inductor current reaches the internally set peak current of typically 400ma. the second criteria that turns off the switch is the maximum on time of 6 s (typ). this is just to limit the maximum on time of the converter to cover for extreme conditions. as the switch is turned off the external schottky diode is forward biased delivering the current to the output. the switch remains off for a minimum of 430ns (typ), or until the feedback voltage drops below the reference voltage again. using this pfm peak current control scheme the converter operates in discontinuous conduction mode (dcm) where the switching frequency depends on the output current, which results in very high efficiency over the entire load current range. this regulation scheme is inherently stable, allowing a wider selection range for the inductor and output capacitor. peak cur rent control the internal switch turns on until the inductor current reaches the typical dc current limit (i lim ) of 400ma. due to the internal propagation delay of typically 100ns, the actual current exceeds the dc current limit threshold by a small amount. the typical peak current limit can be calculated: tieo :x]t; l pmq e mr h srr?? i li m = 400m a the high er the input voltage and the lower the inductor value, the greater the peak current. soft-start all inductive step-up converters exhibit high inrush current during start-up if no special precaution is made. this can cause voltage drops at the input rail during start up and may result in an unwanted or early system shutdown. the ce8304limits this inrush current by increasing the current limit in two steps starting from i lim /3 for 256 cycles to i lim /2 for the ne xt 256 cycles, and then full current limit. enable pulling the enable (en) to ground shuts down the device reducing the shutdown current to 0.1 a (typ). because there is a conductive path from the input to the output through the inductor and schottky diode, the output voltage is equal to the input voltage during shutdown. the enable pin needs to be terminated and should not be left floating. under- voltage lockout an unde r-voltage lockout prevents misoperation of the device at input voltages below typically 1.5v. when the input voltage is below the under-voltage threshold, the main switch is turned off. thermal shutdow n an internal t hermal shutdown is implemented and turns off the internal mosfets when the typical junction temperature of 155 c is exceeded. the thermal shutdown has a hysteresis of typically 20c. this data is based on statistical means and is not tested during the regular mass production of the ic. leshan radio company, ltd.
? applica tion information inductor selection, maximum l oad current because the pfm peak current control scheme is inherently stable, the inductor value does not affect the stability of the regulator. the selection of the inductor together with the nominal load current, input and output voltage of the application determines the switching frequency of the converter. depending on the application, inductor values between 2.2 h and 47 h are recommended. the maximum inductor value is determined by the maximum on time of the switch, typically 6 s. the peak current limit of 400ma (typ) should be reached within this 6 s period for proper operation. the inductor value determines the maximum switching frequency of the converter. therefore, select the inductor value that ensures the maximum switching frequency at the converter maximum load current is not exceeded. the maximum switching frequency is calculated by the following formula: ? w: qe\; l mr : qm r ; h : syx f mr ; t h h syx where: i p = peak cur rent l = selected inductor value v in (min) = th e highest switching frequency occurs at the minimum input voltage if the selected inductor value does not exceed the maximum switching frequency of the converter, the next step is to calculate the switching frequency at the nominal load current using the following formula: ? w:mpseh; l t h pseh h : syx f mr e b ; t 6 h where: i p = peak cur rent l = selected inductor value i load = nominal load curr ent vd = rectifier diode forward voltage (typically 0.3v) a smaller inductor value gives a higher converter switching frequency, but lowers the efficiency. the inductor value has less effect on the maximum available load current and is only of secondary order. the best way to calculate the maximum available load current under certain operating conditions is to estimate the expected converter efficiency at the maximum load current. the maximum load current can then be estimated as follows: pseh : qe\ ; l t 6 h h? w:qe\;; t h : syx f mr ; where: i p = peak cur rent l = selected inductor value f s(ma x) = maximum switching frequency as calculated previously = expected converter efficiency. typically 70% to 85% the maximum load current of the converter is the current at the operation point where the converter starts to enter the continuous conduction mode. usually the converter should always operate in discontinuous conduction mode. last, the selected inductor should have a saturation current that meets the maximum peak current of the converter. another important inductor parameter is the dc resistance. the lower the dc resistance, the higher the efficiency of the converter. see table 1 and the typical applications for the inductor selection. table 1. recommended inductor for typical lcd bias supply inductor component component 10 h sumida cr32-100 high efficiency 10 h sumida cdrh3d16-100 high efficiency 10 h murata lqh4c100k04 high efficiency 4.7 h sumida cdrh 3d16-4r7 small solution size 4.7 h murata lqh3 c4r7m24 small solution size leshan radio company, ltd.
? application information setting the output vo ltage the output voltage is calculated as: syx l s?trt h ls e 5 6 p for battery- powered applications, a high-impedance voltage divider should be used with a typical value for r2 of 0 200k ? and a maximum value for r1 of 2.2m ? . smaller values might be used to reduce the noise sensitivity of the feedback pin. a feedforward capacitor across the upper feedback resistor r1 is required to provide sufficient overdrive for the error comparator. without a feedforward capacitor, or with one whose value is too small, the ce8304shows double pulses or a pulse burst instead of single pulse at the switch node (sw), causing higher output voltage ripple. if this higher output voltage ripple is acceptable, the feedforward capacitor can be left out. the lower the switching frequency of the converter, the larger the feedforward capacitor value required. a good starting point is to use a 10pf feedforward capacitor. as a first estimation, the required value for the feedforward capacitor at the operation point can also be calculated using the following formula: jj l s t hn h ? w tr h s where: r1 = upper resistor of voltage divider f s = switching frequency of the converter at the nominal load current (see the inductor selection, maximum load current section for calculating the switching frequency) c ff = choose a value that comes closest to the result of the calculation the larger the feedforward capacitor the worse the line regulation of the device. therefore, when concern for line regulation is paramount, the selected feedforward capacitor should be as small as possible. see the following section for more information about line and load regulation. line and load regulation the line regulation of the ce8304depends on the voltage ripple on the feedback pin. usually a 45mv peak-to-peak voltage ripple on the feedback pin fb gives good results. some applications require a very tight line regulation and can only allow a small change in output voltage over a certain input voltage range. if no feedforward capacitor cff is used across the upper resistor of the voltage feedback divider, the device has the best line regulation. without the feedforward capacitor the output voltage ripple is higher because the ce8304shows output voltage bursts instead of single pulses on the switch pin (sw), increasing the output voltage ripple. increasing the output capacitor value reduces the output voltage ripple. if a larger output capacitor value is not an option, a feedforward capacitor c ff can be used as described in the previous section. the use of a feedforward capacitor increases the amount of voltage ripple present on the feedback pin (fb). the greater the voltage ripple on the feedback pin ( 1 45mv), the worse the line regulation. there are two ways to improve the line regulation further: 1. use a smaller inductor value to increase the switching frequency which will lower the output voltage ripple, as well as the voltage ripple on the feedback pin . 2. add a small capacitor from the feedback pin (fb) to ground to reduce the voltage ripple on the feedback pin down to 45mv again. as a starting point, the same capacitor value as selected for the feedforward capacitor c ff can be used. en pin protection power input v in may exhibit ver y high voltage spike (> 2 v in ) under certain situations such as hot swap or hot-insertion. in order to prevent ce8304from being damaged by high voltage spike and protect en pin during power-on, when connecting en to v in , a p ull-up resistor (> 1k ) is recommended to be added between en and vin instead of connecting them directly (figure 1). output capacitor selection for best output voltage filtering, a low esr output capacitor is recommended. ceramic capacitors have a low esr value but tantalum capacitors can be used as well, depending on the application. leshan radio company, ltd.
assuming the converter does not show double pulses or pulse bursts on the switch node (sw), the output voltage ripple can be calculated as: ? syx l syx syx hf s ? w : msyx ; f t h syx e b f mr g e t h where: ip = peak current l = selected inductor value i out = nominal load curre nt f s(iout) = switching frequ ency at the nominal load current as calculated previously v d = rectifier diode forwa rd voltage (typically 0.3 v) c out = selected output capacitor esr = output capacitor esr value input capacitor selection for good input voltage filtering, low esr ceramic capacitors are recommended. a 4.7 f ceramic input capacitor is sufficient for most of the applications. for better input voltage filtering this value can be increased. diode selection to achieve high efficiency a schottky diode should be used. the current rating of the diode should meet the peak current rating of the converter as it is calculated in the peak current control section. use the maximum value for ilim for this calculation. layout considerations typical for all switching power supplies, the layout is an important step in the design, especially at high peak currents and switching frequencies. if the layout is not carefully done, the regulator might show noise problems and duty cycle jitter. the input capacitor should be placed as close as possible to the input pin for good input voltage filtering.b the inductor and diode should be placed as close as possible to the switch pin to minimize the noise coupling into other circuits. because the feedback pin and network is a high-impedance circuit, the feedback network should be routed away from the inductor. the feedback pin and feedback network should be shielded with a ground plane or trace to minimize noise coupling into this circuit. wide traces should be used for connections. a star ground connection or ground plane minimizes ground shifts and noise. leshan radio company, ltd.
? p ackaging information z sot23-6 package outline dimensions symbol dimensions in millimeters dimensions in inches min max min max a 1.050 1.250 0.041 0.049 a1 0.000 0.100 0.000 0.004 a2 1.050 1.150 0.041 0.045 b 0.300 0.500 0.012 0.020 c 0.100 0.200 0.004 0.008 d 2.820 3.020 0.111 0.119 e 1.500 1.700 0.059 0.067 e1 2.650 2.950 0.104 0.116 e 0.950(bsc) 0.037(bsc) e1 1.800 2.000 0.071 0.079 l 0.300 0.600 0.012 0.024 0 8 0 8 leshan radio company, ltd.
z sot23-5 package outline dimensions s ymbol dimensions in m illimeters dimensions in inches min. max. min. max. a 1.050 1.250 0.041 0.049 a1 0.000 0.100 0.000 0.004 a2 1.050 1.150 0.041 0.045 b 0.300 0.500 0.012 0.020 c 0.100 0.200 0.004 0.008 d 2.820 3.020 0.111 0.119 e 1.500 1.700 0.059 0.067 e1 2.650 2.950 0.104 0.116 e 0.950( bsc) 0.037(bsc) e1 1.800 2.000 0.071 0.079 l 0.300 0.600 0.012 0.024 0 e e 8 e 0 e 8 e leshan radio company, ltd.
z dfn2x2-6 package outline dimensions s ymbol dimensions in millimeters min. nom. max. a 0.70 0.75 0.80 a1 0.00 0.02 0.05 a2 0.50 0.55 0.60 a3 0.20ref b 0.20 0.25 0.30 d 1.90 2.00 2.10 e 1.90 2.00 2.10 d2 0.70 0.80 0.90 e2 1.20 1.30 1.40 e 0.55 0.65 0.75 h 0.25ref k0.20- - l 0.30 0.35 0.40 r0.1 1- - leshan radio company, ltd.

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